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Ultra-Wideband Bandpass Filter Using Step-Impedance Resonator (SIR)

Parent Category: 2017 HFE

By Shirish Karveer

Abstract— This paper presents a compact ultra- wideband (UWB) bandpass filter (BPF) using step- impedance resonators (SIR). The operating frequency range is chosen to fall within the lower UWB spectrum of 3.1 GHz to 10.3 GHz. The passband has a center frequency is 4 GHz.  The proposed BPF generates a single   passband   located   at   the   desired   frequency through a single filter circuitry.

The proposed filter is constructed by combination of two highly compact wideband bandpass filters (BPFs) with different physical dimensions which are designed on the basis of a folded-T-shaped stepped impedance resonator (SIR) and parallel coupling feed structure. The wideband BPFs can be designed separately, and the design procedure is described. The narrow notched band with 3.8% 3 dB fractional bandwidth (FBW) from 5.15 to 5.35 GHz (IEEE 802.11a lower band) is created in order to eliminate interference from wireless local area network (WLAN) with the determined UWB passband. The center frequency and bandwidth of the notched band can be controlled by tuning the structural parameters. The full-wave EM simulated and measured results are in good agreement, showing that the proposed filter possesses good characteristics including wide passband, high selectivity, low insertion loss, large notch deep and sharp rejection.

Introduction

The ultra-wideband (UWB) radio system has been receiving great attention from both academy and industry since the Federal Communications Commission (FCC)'s release of the frequency band from 3.1 to 10.6 GHz for commercial communication applications in February 2002 [1]. To realize such a UWB radio system, an UWB bandpass filter is one of the key passive components, with the requirements to be ultra-wideband, to have low insertion loss over the band as a conventional filter, to have good performance at  low  frequency  end  outside  the  operating band to meet FCC's limit, and at the same time to have a good group delay performance, which is strongly required for an impulse radio system to keep the distortion of pulse shape of the short pulses minimum. Although developing such a filter is definitely a challenging work, we have successfully invented a novel simple and compact planar filter structure which exhibits very excellent UWB filtering performance [2].

Resonance Characteristics Of SIR 

Figure.1 presents the evolution of folded-T-shaped stepped impedance resonator from conventional model stage by stage, which for more compactness the narrow section in conventional SIR is converted to two parts as in Figure 1 and then is folded back towards the wider section. As discussed in [7], based on transmission line theory, the equivalent circuit for the conventional open-circuited stepped impedance resonator shown in Figure.2 can be approximated as a series LC resonator. As indicated in Figure 2, the conventional open-circuited SIR is constructed by two sections with different characteristic impedances, the narrower line section with characteristic impedance Z1 and electrical length ѳ1 and wider line section with characteristic impedance Z2 and electrical length ѳ2.

1701 HFE sir fg01

Figure 1 • Evolution of folded-T-shaped SIR from conventional model.

1701 HFE sir fg02

Figure 2 • Equivalent circuit model of an open-circuited SIR.

1701 HFE sir eq01   (1)

Let Zin to zero, the resonance condition can be derived by:

1701 HFE sir eq02   (2)

where Rz = Z2/Z1 is the impedance ratio of the SIR.

The fundamental and higher order resonant frequencies can be adjusted over a wide frequency range with tuning of the Rz and length ratio U defined as

1701 HFE sir eq03(3)

When ѳ ѳ1 = ѳ2 = ѳ0, it can be obtained from (2).

1701 HFE sir eq04(4) 

And the ratio of fundamental and second harmonic resonance frequencies f0, fs1, with corresponding electrical lengths ѳѳ0 and ѳѳs1 respectively, can be defined as [7]

1701 HFE sir eq05(5) 

This implies that by appropriately determining the impedance ratio Rz, it is possible to achieve two resonant frequencies with any desired ratio for applications such as dual-band filter. However, dependent on the choice of U and Rz, it is feasible to couple different resonant modes to obtain a wide passband. For instance, it was found that when considering that f0 = 4 GHz and fs1 = 5.8 GHz with Rz =0.25, the length ratio U can be explicitly determined as nearly 0.65 to achieve the desired wideband [5, 6].

Ultra-Wideband Bandpass Filter Including Narrow Notched Band

By utilizing the proposed wideband BPF discussed in the previous section, an ultra-wideband bandpass filter with good performances and highly rejected notched band can be designed and simulated. The configuration of the designed notched band UWB filter is shown in Figure 3. To achieve very wide passband with bandstop notch characteristics, the proposed wideband BPFs.

1701 HFE sir fg03

Top view and Back view

1701 HFE sir fg04

1701 HFE sir fg05

Figure 3 • Schematic of designed notched band UWB BPF. 

1701 HFE sir fg06

Figure 4 • Copper part (shown in pink color) of designed notched band UWB BPF.

1701 HFE sir fg07

Figure 5 • Substrate part  (shown  in  Green color)  of designed notched band UWB BPF.

1701 HFE sir fg08

Figure 6 • Assign a Line Voltage source (two ports) of 1Volt at a zero phase angle (shown in blue cones) to designed notched band UWB BPF.

The simulated S21 for wideband BPF is shown in Figure 7 individually and as a whole structure, hence, the mechanism of creating UWB passband with bandstop notch and transmission zeros at the lower and upper sides of passband edges can be discovered. By tuning structural parameters and spacing S, the notch response can be adjusted. It can be seen in Figure 8 that as the D1 length increases from 8.5 to 10mm with steps of 0.5mm while D2 and S remain 16.5 and 0.14 mm, respectively, the notch 3 dB bandwidth slightly increases from 0.74% to 12.52% and notch shifts to lower frequency with larger rejection level.

1701 HFE sir fg09

Figure 7 • Simulated (S11,  S12,  S21  and  S22) results  of wideband BPF.

However, from Figure 8 as the D2 length decreases from 17.5 to 16mm with steps of 0.5mm while D1 and S remain 9.2 and 0.14 mm, respectively, the notch 3 dB bandwidth slightly increases from 1.02% to 6.54%, and the notch shifts to higher frequency with larger rejection level. The major reason for this behavior is that by tuning D1 and D2, the resonant frequencies of the folded-T-shaped SIRs will change. The spacing S has considerable influence on the bandwidth and the rejection level of the notch. Figure 8 depicts the simulated results of the rejection characteristics as a function of S. By increasing S, as a result of weak coupling, the notch bandwidth decreases, and the rejection level becomes lower. In order to evaluate frequency performance of the designed notched band UWB BPF, the filter is simulated by Singula Software (http://www.integratedsoft.com/Products/Singula)

1701 HFE sir fg11

Figure 8 • Tuning structural parameters.

1701 HFE sir fg12

Figure 8 • Simulated (VSWR Vs frequency for port1 and port 2) results of wideband BPF.

1701 HFE sir fg13

Figure 9 • Simulated S21 results of wideband BPF.

1701 HFE sir fg14

Figure 10 • Simulated S11 results of wideband BPF.

Conclusion

Utilizing folded-T-shape model of stepped-impedance resonator, a compact wideband bandpass filter has been developed and introduced. Combining the proposed wideband bandpass  filters  with  different  physical dimensions   was   used   to   corroborate   ultra-wideband bandpass filter with notched band characteristics. The proposed filter realizes very wide passband with 101.95% 3 dB FBW including a narrowband stop notch with 3.8% 3 dB FBW at the center frequency of 5.25 GHz with large deep in order to eliminate interference from wireless local area network (WLAN) with the determined UWB passband. Compared to the existing notched band filter designs in the literature the proposed filter has simple structure, compact size,   high   performance,   and   easy   fabrication.   These attractive features make the design suitable for employing in advanced UWB wireless communication systems.

References

1. Deng, H.-W., Y.-J. Zhao, X.-S. Zhang, L. Zhang, \Compact quintuple-mode UWB Bandpass filter with good out-of-band rejection," Progress In Electromagnetic Research Letters, Vol. 14, 111{117, 2010.

2. Federal Communications Commission (FCC), \Revision of part 15 of the commission's rules regarding ultra-wideband transmission systems," First Report and Order, ET-Docket 98{153, FCC 02-48, Apr. 2002.

3. Li, R. and L. Zhu, \Compact UWB bandpass filters using stub-loaded multiple-mode resonator,” IEEE Microwave. Wireless Components. Lett., Vol. 17, No. 1, 40{42, Jan. 2007.

4. Huang, J.-Q. and Q.-X. Chu, \Compact UWB band-pass filter utilizing modified Composite right/left-handed structure with cross coupling," Progress In Electromagnetics Research, Vol. 107,179{186, 2010.

5. Naghshvarian Jahromi, M. and M. Tayarani,\Miniature planar UWB bandpass filters with circular slots in ground," Progress In Electromagnetics Research Letters, Vol. 3, 87{93, 2008.

6. Shobeyri, M. and M. H. Vadjed-Samiei, Compact ultra-wideband bandpass filter with defected ground structure," Progress In Electromagnetics Research Letters, Vol. 4, 25{31, 2008.

7. Hsu, C.-Y., H.-R. Chuang, and C.-Y. Chen, Compact microstrip UWB dual-band bandpass filter with tunable rejection band," Journal of Electromagnetic Waves and Applications, Vol. 23, Nos. 5{6, 617{626, 2009. A. Saito, H. Harada and A. Nishikata, “Development of bandpass filter for ultra-wideband (UWB) communication systems,” 2003 IEEE Conference on Ultra Wideband Systems and Technologies, pp. 76-80, Nov. 2003.

8. H. Ishida and K. Araki, “A design of tunable UWB filters,” 2004 International Workshop on Ultra Wideband Systems, pp. 424-428, May 2004.

9. J.-T. Kuo and E. Shih, “Wideband bandpass filter design with three-line microstrip structures,” 2001 IEEE MTT-S Int. Microwave Symp. Dig., pp. 1593-1596.

10. K.-S. Chin, L.-Y. Lin and J.-T. Kuo, “New for- mulas for synthesizing microstrip bandpass filters with relatively wideband widths,” IEEE Microwave and Guided Wave Letters, vol.14, pp.231-233, March 2004.

11. J. M. Drozd and W. T. Joines, “Maximally flat quarter wavelength-coupled Transmission-Line filters using Q distribution,” IEEE Trans. Microwave Theory Tech., vol. 45, no.12, pp.2100-2113, Dec. 1997.

12. INTEGRATED’s software, Singula, 2012.

13. W. W. Mumford, “Tables of stub admittances for maximally flat filters using shorted quarter- wave stubs,” IEEE Trans. Microwave Theory Tech., vol. 13, pp.373-376, Dec. 1965.

About the Author

Shirish Karveer is a Testing and Benchmarking Engineer with INTEGRATED Engineering Software.

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